Wave length modulator and control means



Aug. 7, 1945. v M. G. CROSBY 2,380,947

WAVE LENGTH MODULATOR AND CONTROL MEANS Filed May 14, 1941 5 sheets-sheet 1 INVENTOR ATTORNEY Aug. 7, 1945.'

M. G. CROSBY- WAVE LENGTH MODULATOR ND CONTROL MEANS- Fled May 14, 1941 5 Sheets-Shes?l 2 nounou INVENTORG url-ng BY AroRNEY @Jh ,ig

Aug- 7, 1945. M. G. CRQSBY 2,380,947

WAVE LENGTH MODULATOR AND CONTROL MEANS Filed May 14, 1941 5 Sheets-Sheet 5 A Aww V@ if@ 4a lime,

F/Zecr Vvvvvvvv ATTORNEY Patented Aug, 7, 1945 funn-ay G. cmby, Riverhead, 'N. y., mmm u Radio Corporation of America, a corporation of Delaware application my 14, mi, serial '17 Claims.

- control and remote tuning. The circuit has the advantages of extreme simplicity together with all-electronic control and high control sensitivity. v In one modification phase inversion of alternating current is obtained by a pair of tubes each having a grid excited by the said automatic control with a control potential on another grid and the anodes connected in parallel s o that the output depends on the polarity of the control potential. One modication is a simplified version which obtains its simplicity by means of the application of a novel eil'ect taking place in a pentode when the screen resistor is unbypassed. I have found that when the proper value of unbypassed resistor is used in a two-grid tube of the 6SA7 type the phase of the'voltage ampli`fied by the first 4grid is reversed. At the same time the phase relation of the third grid is unaffected so that if voltages of the same phase are fed to the two grids, they will oppose in the quency of a reactance-tube modulated oscillator' output, or plate, circuit. This makes possible is stabilized by means of automatic frequency control. The automatic frequency control described brieily above utilizes my novel type of lmotor-driven condenser and frequency-discriminating circuits which do not depend upon tuning.

Thus the' frequency-controlled oscillator is held 4,

to: the same frequency as the master'reference 4 oscillator instead of to a constant beat frequency difference. 'I'his makes the modulator frequency independent of any tuning except that'of the -reference oscillator.

tain automatic frequency control potentials, or

the modulated oscillator was applied directly to a crystal discrimlnator for detection of the automatic frequency control potentials. Furthermore, the prior circuits utilised the modulating reactance-tube as the device to apply the frequency correction for drift as well as for modulation; in the circuits to be described here, a motor-driven condenser is employed.

In the modulatorof the present disclosure a frequency discriminator is utilized in which the reference oscillator is combined with the modulated .oscillator and the phase modulated component of the beat frequency is detected. 'I'his detected output has a wave form which has sharp positive peaks when the modulated oscillator is on one side of the reference oscillator, ,and sharp negative peaks when the modulated oscillator is on the other side of the reference oscillator. Hence by feeding this detected output to a detecting system which detects the op posite hall' cycles differentially, a potential` is obtained which is positive when the modulator frequency is on one side of the reference frequency and is negative when the modulator frequency is on the other side of the reference frequency. This potential is'applied as the automatic frequency central' potential to the control grid or grids cfa tube or tubes in a phase reversing circuitl which controls the direction ofrotation of a condenser across the tuning of the modulator.

Amotor the direction of rotation of which is con- .trolled lin a novel manner in accordance vwith my invention.

Frequency modulators of the prior art, of the.

type to be described here, are described in my United States applications Serial No.` 135,578, `flied April 13, 1937, now U. S. Patent No. 2,279,659, dated April 14, 1942, Serial No. 312,446, filed January 5, 1940, now U. B. Patent No. 2,379,660, dated April 14, 1942, and Serial'No. 355,592, flied 6, 1940 now U. B. Ptellt No. 2,312,079, Ii rangement 0f Figure 3.

Figure 2 illustrates a modification of the arrangement of Figure 1. f

Figure-3 illustrates my novel alternating current phase reverser and motor in a wave length modulation system.

Figures 4A to4D are curves used in describing the operation of my system. while Figure 5 is a modification of the circuit ar- Figure l shows an embodiment making use of the principle of the balancing action, obtainable in a two-grid tube, in a control circuit. In this circuit, tubes I and 2 serve as amplifiers to amplify the voltage fed to one winding of motor 3 while the other winding is continuously connected to the alternating line voltage throulh phase-shifting condenser I. The purpose of condenser l is to produce a phase quadrature relation between the currents in the motor windings 5 and I2.

Alternating current voltage or a frequency the same a's that applied to winding 5 and of a phase such that the lalternating current in winding 82 is substantially in quadrature with that in winding i is applied to terminals A and B to produce a potential across potentiometer resistance Il which is lapplied to grid GI and also by way of condenser I4 and resistance Il to grid G2. A control voltage is fed to terminal C and thence to grid G3. The cathode is connected to groimd by a cathode bias resistance I2. The screen grid G4 is charged positive with respect to the cathode by unbypassed resistor II and, as pointed out hereinbefore. when the proper value oi' unbypassed resistor is used in' the screen grid direct current circuit of a two-grid tube of the proper type, the phase of the voltage ampliiied by the rst grid is reversed. At the same time the phase relation of the third grid is unaffected, so that if voltages of the same phase are fed to the two grids, they will oppose in the output or plate circuit. By relatively controlling the amplification of the voltages fed to the anode by the two-grids, one or the other thereof can be made large so that it is no longer balanced out in the output,

circuit. In this manner phase reversal or inversion of an alternating current is obtained Tube I ampliiies the alternating current, while reversing its phase, and the current is supplied by anode IB and 'resistance Il and coupling condenser 2n'to the grid 22 oi' tube 2. The control grid 22 of tube 2 is biased negative by cathode resistance 2l and grid resistance 26. The anode 30 is connected to the winding 32 of motor 3. This winding is shunted by a condenser Il which tunes the winding 32 to resonance. The screen grid Il is charged positive by a direct current circuit asados? tubes and circuit element constants listed herein. However, the following are a typical set of experimentally determined circuit constants used in the circuit of Figure 1: Tube I is a 88A7, tube 2 a 6AG7 and the motor a Bodine Dynamic Braking Type KCI. The voltage applied to GI is about 0.6 volt with about one-half that value lcd to G2. The motor starts with plus or minus 0.17 volt applied to the control terminal C. Resistor I2=1500 ohms. Resistor I I=150,000 ohms. .tesistor 2l=0.5 megohm. Resistor 2I= 80 ohms. Resistor 2l=20,000 ohms. Condenser 2l=0.l microfarad. Condenser 32:1.0 micrcfarad. Condenser 24:1.0 microiarad. Total plate current drain from the 250 volt supply is about 35 milliamperes. The alternating current applied at A and B may be tube filament voltage or the same reduced to about one volt. This altemating current may be supplied from the same source supplying winding l as in Fig. 3.

The control potential applied at C may be of anynature. For example, the said control potential may represent the deviation in frequency of a radio wave being amplified and the motor I through resistance 2l which is bypassed b'ycondenser 38.

In the absence of control voltage at the control terminal C potentiometer I5 is adjusted so that the voltage amplified by GI exactly balances out the voltage ampliiied by G2 in resistor Il. Under this condition, there will be no voltage fed through ampliiler 2 to winding I2 of the motor so that the shaft SH will not rotate. If a positive voltage is applied to the control terminal C. the balanced condition in tube I is upset and a volt'- age having a phase corresponding to that ampliiied by G3 is repeated in tube 2 and supplied to the motor winding 32. This causes the motor to rotate in a direction depending upon the rel-` ative polarities oi' windings 32 and l. If a negative voltage is fed to the control terminal C, the voltage amplified by GI predominates in the output of tube I. 'I'his voltage has a phase opposite to that amplified by G3 so that the direction of rotation of thel rotor is reversed. Thus it can be seen that the direction of rotation, and stop- Dini. of the motor is under control of, the potentials applied to the control terminal C.

Various tube combinations and circuit element values may be used in my system and I do not propose hereby to limit the same to the particular Vmay tune the said amplifier to the wave ampliiled or the control potential may represent the deviations in mean frequency of a wave length modulated oscillator in which case the motor drives a tuning element in the said oscillator circuit to stabilize said mean frequency of operation. i

controlling grid Gl is grounded and the grid GI' receives the control potentials, but if desired. push-pull ccntrollingpotentials may be applied to both grids. Resistors R and R' and condensers CI and C2 form the phase shifters to shift the phase 90 .degrees so that a phase quadrature relationbetween the currents in windings 5 and 32 is produced. The anodes Il and Il of tubes Il and are tied together and connected to output resistance. Il. The alternating current is amplified by a tube 2 as in Figure 1 and ted to winding 32.

Potentiometer 42 is used to balance the amplitudes of the alternating current inputs to the grids G2 and G3 of the two tubes. This balance is obtained by closing switch S and adjusting for minimum deflection on the electron-ray indicator tube 6I. This indicator tube is placed across the terminals of the motor winding 22 which receive the controlled voltage so that its minimum deflection will indicate balance of the two tube inputs, and full deflection will indicate full voltage applied to the motor terminals. The cathode and screenresistors I9 and II of the two reverser tubes i0 and 60 are common and unbypassed The motor winding' 321s connected directly across the output choke 2| connected to the anode III of the power amplifier 2 without the use of a blocking condenser to eliminate'direct current iiow through the motor windings. The small amount of direct current that iiows through the motor winding l2 with this connection does not appreciably change the operation of the motor. As in Fig. l condenser Il may tune the4 winding I2 to resonance.

This control circuit is very sensitive to control potentials. A `control voltage of plus or minus absence of control potential these tubes give no output. Plus or minus voltageon one of the control vgrids unbalances the relative gains so that the phase of the output voltage depends upon polarity of the control potentials. For the circuit shown, a control voltage of plus or minus 0.06 volt will start the motor in either direction.

The R, C circuits in the grid circuits of the two type SSA'I' tubes 59 and 80 are phase shifters to give the necessary 90 degree phase shift between the voltages fed to the two windings. Switch S shorts out the control potentials so that .potentiometer point P may be adjusted to balance the inputs to the two 6SA7's. The type 66 tube 65 is used to indicate when the motor is running. v

The circuit of Figure 2 operated well when used in an automatic frequency control system in a receiver with the discriminating circuit sup- -tube types 6SA7 at 50 and 69, tube type GAG? at 2 and a tuning tube type 6U5 at 65, with 6.3 volts` alternating current applied at points X and Y. This voltage may be derived from the filament winding on an A.C. transformer. Resistances 4I, 42 and 53 areveach 1000 ohms. vResistances n plying the control potentials at C with the motor f I controlling the tuning of a receiver circuit. The vcircuit elements were of the following values using R and R are each .25 megohm. Resistance 48, f

.l megohm. Resistance 49, 800 ohms. Resistance Il, .v2 megohm. Resistances I8 and 26, .5 megohm. Resistance 24, 40 ohms.l Resistance 2l, 20,000 ohms. Resistances 1I and 13 each one megohm. Condensers CI and C2, .1 rnicrofarad.`

Condensers 20, 61 and 68, .01 microfarad. Condenser 34 is 1 or 2 microfarads. This condenser is preferably such as to tune the plate motor winding 32 to resonance with respect to the applied alternating current, .06 volt applied at C to the grid G3.

As stated above my novel control means is suitable for many uses and is particularly suitable for use in the automatic frequency control circuits of a wave length modulator. When so used a discriminator circuit excited by voltages of a frequency which varies with variations 'in the mean frequency of the generated wave length modulated waves supplies the control potential applied at C. Thus the motor controls the mean tuning of 4the oscillator instead of the same being controlled by the reactance tube as in my United States application Serial No. 135,578, filed April 13, 193'7, now U. s. Patent No. 2,279,659, dated April 14, 1942. This system controls the mean frequency of the'generator quite accurately and has an added advantage in that the frequency control means rests in its last position when the automatic control system fails. Since it is independent of-the reactance tube modulatorof the system a smaller degree of reactance tube control may be used and stability lies more in the oscillatcr circuits and not so much in the reactance tube circuits.

`Figure 3 shows a specific embodiment of my novel phase reverser and control motor in a novel wave length modulation system in which a frequency modulation detector is used in the discriminator circuit for obtaining the automatic frequency control potentials. Tubes 10 and 12 are reactance-tube modulators which push-pull modulate oscillator 80. Tube 10 provides a capacitive eifect with feedback phase shifter C3,.R2. Tube 12 provides an inductive effect with phase shifter L, R3. The reactances of C3 and L are normally made large compared to the resistance of R2 and R3. 16 is a blocking condenser. The oscillator is of the regenerative type and has a tank circuit 18 which includes as a part of its reactance the reactive effects produced in a well yknown manner in reactance tubes 10 and 12. These reactance tubes have their conductances modulated in push pull by potentials from 14 so 'that their reactive effects, one inductive, the other capacitive, increase and decrease in phase opposition. The e'ective capacity and inductance increase and decrease in phase, andsince they are of thev oscillator circuit the wave length of the oscillations generated is modulated. Similar generating and modulating means have been disclosed in my United States application Ser. No. 209,919, filed May 25, 1938, now U. S. Patent No. 2,250,095, dated July 22, 1941, and in my United States application Serial No, 312,446, tiled January 5, 1940, now U. S. Patent No. 2,279,660, dated April 14, 1942.

Part of the output of oscillator 80 is linkcoupled by windings 82 and. to the input circuit 86 of limiter tube 88. The output of the reference oscillator 90 is also fed by winding 92 to the input of the limiter 88. l The relative amplitudes of these two voltages fed to the limiter are adj-usted to be very nearly equal so that the wave form of the frequency modulation component of the resultant is sharply peaked as shown in Fig..

ure 4C. With a given ratio, of these two voltages,

the wave form of Figure 4C will be obtained when the modulated oscillator is on one side of the reference oscillator frequency, and the form of Figure 4D when it is on the other side. This phe- `nomenon is more completely described in my paper,.Frequency Modulation Noise Characterlstics, published in the April. 1937 issue of the Proceedings of the Institute of Radio Engineers. Figure 4 of that paper shows the wave forms which have been calculated from the combination of a carrier and a single sinusoidal interference frequency. If the ratio of the relative arnplitudes of the two voltages fed to the'limiter is reversed, the relative wave forms of Figures 4C and 4D are also transposed. This latter feature provides one method of reversing the direction of the automatic frequency control potentials which this type of detection supplies. The output of limiter 88 is fed to transformer 94 which is connected to multi-grid detector 96 in a manner to detect the frequency-modulation component of the limiter resultant. The voltage from the anode 89 of tube 88 is fed by way of reactive circuits 9| and 93, having a retarding effect,l to grid 95 and also directly by blocking condenser 91,to grid 99. This type of detector is more completely described in my United States application Serial No. 328,353, filed April 6, 1940, now U. S. Patent No. 2,296,090, dated September 15, 1942. The detected output of this detector has the wave forms of Figure 4C or 4D depending upon which side of the reference oscillator frequency the modulated oscillator is located. Voltage amplifier B ampliiies this output and passes it through push-pull transformer |00 to differential diodes |02 and |04. One of these diodes rectifies the positive half cycles of the wave and the other the negative half cycles. Thus, if the wave were as shown in Figure 4C, it is apparent that the detector receiving the positive half cycles corresponding to the sharp peaks would receive the largest voltage and a differential output would appear across the diode resistors |0| and |03.

Battery |05 applies a small negative bias to the diode plates so that only the voltage above the dotted line in Figures 4C and 4D will be detected. Under this condition, the flattened part of the cycle will not draw any diode current at all, but the sharp peaks will exceed the bias and draw current. This bias thus increases the amount of diiferential voltage available. I have found experimentally that this bias is not a necessity to the operation of the rectifiers since practically the same operation was obtained with it as without it. However, this bias may be used to produce an idle range of the control potentials so that the olf-frequency deviation will have to exceed a certain amount before the control starts to operate. Such an adjustment is sometimes desirable to prevent excessive activity of the control motor for small frequency variations which do not need correction.

The output of the differential rectiflers is passed through time-constant circuit |00 (which removes the potentials due to fast frequency variations) to a motor control circuit as described above. This circuit consists of motor |08, power transformer and tubes 50, 60 and H2. The shaft SH of the motor is coupled through gearbox IB to condenser i8 which forms part oi' the tuning of the modulated oscillator 80.V The motor is of the two-phase type with windings 5 and I2. One of these windings, say 5, is continuously fed 60 cycle voltage from transformer |20 and the other winding is fed a voltage which has a phase displaced by either 90 or 270 degrees with respect to the phase of the voltage fed to said one winding. This variable phase voltage is obtained from tube i2 which is fed by the phase-switching circuit consisting of tubes 50 and 00. These two tubes have their plates tied together by means of condenser |22 and are fed in push-pull by a mid-tapped winding on power transformer |20. Condensers |24 and |26 form 90 degree phase Shifters in conjunction with resistors |28 and |30. Thus by biasing one of the tubes towards cutoff and the other towards its operating point, the phase of the voltage in the common output circuit may be reversed so thatfthe direction of rotation of the motor is reversed. The tubes are of the multi-grid type with one of them having its modulator grid GI grounded and the other having its grid G', fed by the automatic frequency control potentials. Thus as the control potential becomesl for instance, negative, the amplification of tube 60 is lowered. This causes the outputof tube 50 to predominate so that the voltage fed to tube ||2 has the phase of the tube 50 output. A positive bias from the automatic frequency control potential causes the amplification of tube I0 to be raised so that the output o1' tube l0 predominates and tube ||2 receives voltage of a phase corresponding to that fed to tube I0 alone.

I have found that this type of motor control is very effective for frequency control due to the fact that in the absence of control potentials, there is a braking effect applied to the motor by asador? 'l the one winding 5 which has voltage applied to it continuously. This braking effect tends to prevent. over-shooting oi' the motor and allows a higher degree of control without motorboating. The fact that only the power for one winding has to be controlled also aids in simplifying the control equipment.

Figure 5 shows the controlling portion of a circuit oi' the type of Figure 3 in which the detection of the frequency modulation component of the resultant of the two waves is effected by a phase modulation receiver with an audio correction network in its output. Oscillations from the reference oscillator 90 and from the controlled oscillator are as in Figure 3 both fed to the input of the limiter tube 88'. The output of the limiter 88 feeds one grid |38 of multi-grid phase detector |40. The other grid |42 of the detector is fed by oscillations from the unmodulated reference oscillator. Phase adjustment of the oscillations from the reference oscillator is accom plished by means of variable condenser |44 and resistor |46. The limiter 00 thus feeds a resultant modulated in phase to the detector |40, and the reference oscillator 90 feeds to the detector |40 a voltage which may be considered as the synchronized carrier of the phase modulated resultant. The phase shifter |44 and |46 is adjusted for a 90 degree relation between the carrier of the resultant and that furnished by the reference oscillator 90. The phase modulations of the resultant are thus detected and appear on the output resistor |49 of tube |40. The manner in which this detection takes place is wel] known, having been described in my United States Patent No. 2,063,588, dated December 8, 1936. This output has a wave form as shown in Figure 4A when the controlled wave` is on one side of zero beat with the reference oscillator and like Figure 4B when it is on the other side of zero beat. Calculations of this wave form are shown in my paper Communication by Phase Modulation published in the February 1939 issue of the Proceedings of the Institute of Radio Engineers. Figure 14 of that paper shows wave forms for two ratios of amplitude of the two waves. It can be seen that as the ratio of amplitudes approaches equality, the wave form approaches the saw-tooth shape shown in Figure 4A and Figure 4B. When this wave form is passed through the correction network composed of condenser |50 and resistance |52, the correction network passes those parts of the wave having the greatest rate of change, with the greatest amplitude. Thus the waves of Figure 4A and Figure 4B are converted to waves like Figures 4C and 4D, respectively. The rest of the control circuit is the same as that of Figure 3. Tube |50 is a voltage amplifier which may make up for the loss incurred by the use of the correction network. Tube |58 has its anode connected to tube 00, which corresponds to tube 90 of Figure 3.

Either of these control systems may be used for automatic frequency control in a receiver as well as in a modulator as shown. For instance, if the system of Figure 3 were used, the motordriven condenser might tune the high-frequency oscillator of a super-heterodyne receiver and the incoming heterodyned signal would be fed to the limiter on the leads which come from oscillator 00. The control system would then operate to maintain the heterodyned signal at the same frequency as the local reference oscillator.

In my experiments with this type of control system, I have found that the application o! frequency modulation to the oscillator does not interfere with the operation of the control. With modulation present, the carrier is modulated across the zero-beat point so that the wave form is modulated between the condition of Figures 4C and 4D. Thus, if the modulating wave is a sinusoidal wave, the wave form will be like 4C half the time and like 4D the other half when the modulator is properly tuned. This condition produces a balance in the detected output of the dilerential diodes so that no control voltage is obtained. When an off-tune condition is present, the wave form is predominately of one type so that the detected voltage supplies a potential of the right direction for automatic frequency control. Thus the detection of the wave form which is predominant most of the time allows the op eration during the presence of modulation.

I claim:

1. In means for relaying alternating voltages, an electron discharge device having an output electrode, a cathode and two control electrodes, means for applying alternating voltages of substantially like phase to said control electrodes, means for biasing said control electrodes relative to said cathode by biases of such value that voltages of substantially like amplitude are relayed to said output electrode, means for reversing the phase of one of the voltages relayed to said output electrode so that the voltages thereon compensate, and means for varying the potential on one of said control electrodes so that one of said voltages on said output electrode predominates.

2. Means as recited in claim l wherein said phase reversing means is an additional electrode in said devices with an unbypassed impedance for supplying potential thereto.

3. In apparatus for reversing the phase of alternating current comprising a pair of electron discharge tubes each having an output electrode and a plurality of control grid electrodes, connections for applying said alternating current in substantially relatively fixed phases to corresponding control grid electrodes in said tubes, an output circuit connected with the output electrodes of said tubes, said connections including means for producing a relative phase reversal of the voltages supplied to the output circuit by the respective tubes and connections for relaasador:

tively varying the biases on corresponding cony in said tubes, an output circuit connecting the output electrodes of said tubes in parallel, said connections including means for relatively reversing the phase of one of the voltages fed to said output circuit by one tube with respect to the voltage fed to said output circuit by the other tube, and connections for relatively varying the biases on other like control electrodes of said tubes to thereby vary the output` current supplied by the respective tubes.

5. Means for producing alternating current of reversible phase and variable amplitude comprising, an electron discharge device having a cathode, an output electrode in an output circuit and a plurality of control grid electrodes, means for applying alternating current of substantially relatively flxed phases to two of said grid electrodes, means for varying the relative bias of said two control grid electrodes relative to the cathode to thereby control the phase and amplitude o! the alternating current supplied to said output circuit, and means for reversing the phase of one of said output currents.-

6. Means for producing alternating current of reversible phase comprising, an electron discharge device having a cathode, an output electrode in anoutput circuit and a plurality of control grid electrodes, means for applying alternating current of substantially like frequency and phase to two of said grid electrodes whereby amplified voltages appear on said output electrode, means in said tube for reversing the phase of one of said voltages on said output electrode, and means for varying the relative biasu of said two control grid electrodes relative to the cathode to thereby control the phase of the alternating current supplied to said ouput circuit.

7. In a system for deriving alternating voltage of controllable phase from alternating voltage, an electron discharge tube having an anode,l a cathode, and two control grids, circuits for applying said alternating voltage to the two control grids of said tube, circuits for applying biases to said control grids relative to the cathode of said tube such that the desired ampliiication of the voltage applied to each grid is obtained, an unbypassed resistance connecting the screen grid -of said tube to a source` of potential, and an output circuit coupled to the anode of said tube.

8. In a system for deriving alternating voltage of controllable phase from alternating voltage'of substantially fixed phase, an electron discharge tube of the pentode type, circuits for applying said alternating voltage to the first and third grids of said tube, circuits for applying biases to said grids relative to the cathode of said tube such that the desired amplification of the voltage applied to each of said grids is obtained, an unbypassed resistance connecting the screen grid of said tube to a, source of potential, the value of said unbypassed resistance being such that the phase of the voltage amplified by one of said grids is reversed, and an output circuit coupled to the anode of said tube.

9. In a system for deriving alternating voltage of reversible phase from alternating voltage, an electron discharge tube of the pentode type, circuits for applying said alternating voltage to the two control grids of said tube, biasing circuits for applying biases t0 said control grids relative to the cathode of said tube such that the desired amplification of the voltage applied to each grid is obtained in said tube, an unbypamed resistance connecting the screen grid of said tube to a source of direct grid potential, the value of said resistance being such that the phase of the voltage amplified by the iirst grid of the pentode is reversed, an output circuit connected with the anode of said tube, said amplified voltages appearing in said output circuit, and means for aclditionally controlling the bias on at least one of said controlgrids.

10. In a system of the nature described, an electron discharge tube having an anode, a cathode, a, screen grid, and two control electrodes, a source of alternating current, resistive means for applying alternating currents of like phase in relatively adjustable amounts from said source to the two control electrodes, an output circuit including an impedance connected with said anode, an unbypassed impedance connected with said screen grid for applying thereto a potential which is positive with respect to the cathode, direct current biasing circuits connected to each of said control electrodes, and connections for applying a controlling potential to one of said control electrodes.

11. In a. system of the nature described, a pair of electron discharge tubes each having an anode, a cathode. a screen grid electrode and two control electrodes, a source of alternating current, resistive connections connecting corresponding control electrodes of said tubes in pushpull relation to said source, an output circuit including an impedance connecting said anodes in parallel, a direct current circuit including an impedance connected to the screen grids of said tubes, direct current biasing circuits connecting the control electrodes of each of said tubes to the cathodes thereof, and connections for modulating the potential on a control electrode of one tube relative to the potential on the corresponding control electrode of the other tube.

12. In an arrangement of the class described, a source of alternating current, a resistance coupled to said source of alternating current, an electron discharge device of the pentode type having an anode, a cathode. two control grids between said anode and cathode. and a screen grid electrode, connections coupling spaced points on said resistance between a control grid and the cathode of said device for applying to said control grid alternating potential of a ilrst pnase, a coupling between the other of said control grids and said first resistance for applying to said other control grid alternating potential f 21 Phase Substantially the same as said lirst phase, connections for applying a direct current potential to the anode of said device which is positive relative to the potential on the cathode of said device, an unbypassed resistance for applying na potential to the screen grid of said device which is positive relative to the potential on the cathode of said device whereby the phase of the potential amplified by one of the control grids is reversed relative to the phase of the potential amplified by the other control grid and the said potentials oppose in the anode connections, alternating potential amplitude adjusting means in one of the couplings between the control grids and said first resistance for adjusting the relative amplitude of the alternating potentials on said control grids to values such that the amplified alternating potentials substantially cancel in said anode connections, and connections for applying a variable control potential to one of said control grids such that one or the other of said amplified alternating potentials on said anode predominates depending on the value of the control potential.

13. In a phase reverser for deriving from alternating currents, alternating currents of reversible phase, a source of alternating current, a resistance coupled to said source of alternating current, an electron discharge device having an anode, a cathode, two control grids and a screen grid electrode, connections coupling spaced points on said resistance between a control grid and the cathode of said device for applying to said control grid alternating potential o! a, first phase, a coupling between the other of said control grids and said resistance for applying to said other control grid alternating potential of a phase substantially the same as said rst phase, connections to said anode for applying a direct current potential to the anode which is positive relative to the potential on the cathode of said device, an unbypassed resistance connected to the screen grid of said device for applying a potential to the screen grid which is positive relative to the potential on the cathode of said device whereby the phase of the amplied alternating potential resulting from excitation of one of the control grids is reversed relative to the phase of the amplified alternating potential resulting from excitation of the other control grid and the said amplified potentials oppose in the anode connections, amplitude adjusting means in one of the connections between said control grids and said rst resistance, the amplitude of the alternating potentials supplied to the control grids and the bias potentials thereon being such that the amplified alternating potential substantially cancel in said anode connection, and connections for applying a control potential to one of said control grids which varies above and below a bias potential at which said ampliiied potentials in said anode connections cancel so that one or the other thereof predominates.

14, In an arrangement of the class described, a source of alternating current, a resistance coupled to said source of alternating current, an electron discharge device having an anode. a cathode, two control grids between said anode and cathode spaced different distances from said cathode, and a screen grid electrode associated with the control grid nearest said anode, connections coupling spaced points on said resistance between a control grid and the cathode of said device for applying to said control grid alternating potential of a lirst phase, a cathode biasing resistance in the coupling between said rst resistance and the cathode of said device, a coupling condenser between the other of said control grids and said first resistance for applying to said other control grid alternating potential of a phase substantially the same as said first phase, connections including said biasing resistance for applying a direct current potential to the anode of said device which is positive relative to the potential on the cathode of said device. an unbypassed resistance for applying a potential to the screen grid of said device which is positive relative to the potential on the cathode of said device whereby the phase of the amplified alternating potential resulting from excitation of one of the control grids is reversed relative to the phase of the ampled alternating potential resulting from excitation of the other control grid and the said amplified potentials oppose in the anode connections, alternating potential amplitude adjusting means in one of the couplings between the control grids and said first resistance for adjusting the relative amplitudes of the alternating potentials on said control grids to values such that the amplied alternating potentials substantially cancel in said anode connections, and connections for applying a variable control potential to one of said control grids such that one or the other of said amplified alternating potentials on said anode predominates depending on the value of the control potential.

15. In a system for providing alternating current of reversible phase, a source of alternating current, a resistance coupled across said source of alternating current whereby alternating current flows in said resistance and alternating potential is developed thereacross, an electron discharge device having an anode, a cathode, two

controlgrids and a screen grid electrode, a. connection between one end of said resistance and the cathode of said device, a cathode biasing resistance in said connection, a connection coupling the other endof said resistance to a control grid of said device for applying to said control grid alternating potential of a iirst phase, a coupling between the other of said control grids and a point on said first resistance for applying to said other control grid alternating potential of a phase substantially the same as said first phase, connections including said biasing resistance for applying a direct current potential to the anode of said device which is positive relative to the potential on the cathode of said device, an unbypassed resistance connected to said screen grid for applying a direct current potential to the screen grid of said device which is positive relative to the direct current potential on the cathode of said device whereby the phase of the amplified alternating potential resulting from excitation of one of the control grids is reversed relative to the phase of the amplified alternating potential resulting from excitation of the other control grid and the said ampliiied potentials oppose in the anode connections, potential amplitude adjusting means in the connections between said other control grid and said iirst resistance for adjusting the relative amplitude or the potentials on said control grids to values such that the amplified alternating potentials substantially cancel on said anode, and a resistance' for applying a variable control potential to one of said control grids such that one or the other of said amplified potentials on said anode predominates depending on the value of the controlpotential.

16. In apparatus for relaying voltage, an electron discharge device having an output electrode, a cathode, a screen grid and at least two control electrodes, connections for applying alternating voltages from an external source to two of said control electrodes, 'connections for biasing said control electrodes relative to said cathode by potentials such that the voltages relayed to said output electrode are of substantially equal values, an unbypassed resistor connected to said screen grid for supplying positive potential thereto and a connection for applying a variable control potential to one of said control electrodes whereby the said voltages relayed to said output electrode are relatively varied in amplitude.

17. In a system of the nature described, an electrode discharge device having an output electrode, a screen grid, a cathode and at least two control electrodes, connections for applying voltages of substantially like phase from an external source to two of said control electrodes, connec tions for biasing said control electrodes relative to said cathode and adjusting the relative amplitudes of said applied voltages to such values that the voltages are of substantially equal amplitude on said output electrode, a connection including an impedance for applying a positive potential to said screen grid, and a connection for applying a control potential to one of said control electrodes whereby one of the voltages relayed to said output electrode predominates.

MURRAY G. CROSBY. 

